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Электронный компонент: CS4329

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1
Copyright
Cirrus Logic, Inc. 1998
(All Rights Reserved)
Cirrus Logic, Inc.
Crystal Semiconductor Products Division
P.O. Box 17847, Austin, Texas 78760
(512) 445 7222 FAX: (512) 445 7581
http://www.crystal.com
CS4329
20-Bit, Stereo D/A Converter for Digital Audio
Features
l
20-Bit Conversion
l
115 dB Signal-to-Noise-Ratio (EIAJ)
l
Complete Stereo DAC System
- 128X Interpolation Filter
- Delta-Sigma DAC
- Analog Post Filter
l
106 dB Dynamic Range
l
Low Clock Jitter Sensitivity
l
Filtered Line-Level Outputs
- Linear Phase Filtering
- Zero Phase Error Between Channels
l
Adjustable System Sampling Rates
- including 32 kHz, 44.1 kHz & 48 kHz
l
Digital De-emphasis for 32 kHz, 44.1 kHz, &
48 kHz
l
Pin-compatible with the CS4390
Description
The CS4329 is a complete stereo digital-to-analog out-
put system. In addition to the traditional D/A function, the
CS4329 includes a digital interpolation filter followed by
an 128X oversampled delta-sigma modulator. The mod-
ulator output controls the reference voltage input to an
ultra-linear analog low-pass filter. This architecture al-
lows for infinite adjustment of sample rate between 1 and
50 kHz while maintaining linear phase response simply
by changing the master clock frequency.
The CS4329 also includes an extremely flexible serial
port utilizing mode select pins to support multiple inter-
face formats.
The master clock can be either 256, 384, or 512 times
the input sample rate, supporting various audio
environments.
ORDERING INFORMATION
CS4329-KP
-10 to 70 C
20-pin Plastic DIP
CS4329-KS
-10 to 70 C
20-pin Plastic SSOP
CDB4329
Evaluation Board
I
LRCK
AUTO_MUTE
DGND
DIF0
MUTE_L
20
16
5
11
7
SCLK
9
SDATA
10
DIF1
19
DEM0
1
DEM1
2
MCLK
8
AGND
4
VA
VD
AOUTL+
18
AOUTR+
14
Serial Input
Interface
Interpolator
Interpolator
De-emphasis
Delta-Sigma
Modulator
Delta-Sigma
Modulator
DAC
DAC
Voltage Reference
Analog
Low-Pass
Filter
Analog
Low-Pass
Filter
DIF2
12
3
6
AOUTL-
17
AOUTR-
13
MUTE_R
15
APR `98
DS153F1
CS4329
2
DS153F1
ANALOG CHARACTERISTICS
(T
A
= 25C; Full-Scale Differential Output Sine wave, 997 Hz; Fs =
48 kHz; Input Data = 20 Bits; SCLK = 3.072 MHz; MCLK = 12.288 MHz; R
L
= 20 k
differential; VD = VA = 5 V;
Logic "1" = VD; Logic "0" = DGND; Measurement Bandwidth is 10 Hz to 20 kHz, unweighted unless otherwise
specified.)
Parameter
Symbol Min Typ
Max
Unit
Specified Temperature Operating Range
T
A
-10
-
70
C
Dynamic Performance
Dynamic Range
20-Bit
(Note 1)
(A-Weighted)
18-Bit
(A-Weighted)
16-Bit
(A-Weighted)
98
101
-
-
-
-
103
106
101
104
94
96
-
-
-
-
-
-
dB
dB
dB
dB
dB
dB
Total Harmonic Distortion + Noise
(Note 1)
20-Bit
0 dB
-20 dB
-60 dB
18-Bit
0 dB
-20 dB
-60 dB
16-Bit
0 dB
-20 dB
-60 dB
THD+N
-90
-78
-38
-
-
-
-
-
-
-97
-83
-43
-96
-81
-41
-93
-74
-34
-
-
-
-
-
-
-
-
-
dB
dB
dB
dB
dB
dB
dB
dB
dB
Idle Channel Noise / Signal-to-Noise-Ratio
(Note 2)
-
115
-
dBFS
Interchannel Isolation
(1 kHz)
-
-110
-
dB
Combined Digital and Analog Filter Characteristics
Frequency Response 10 Hz to 20 kHz
(Note 3)
-
0.1
-
dB
Deviation from linear phase
-
0.5
-
deg
Passband: to -0.1 dB corner
(Note 3)
0
-
21.77
kHz
Passband Ripple
-
-
0.001
dB
StopBand
(Note 3)
26.23
-
-
kHz
StopBand Attenuation
(Note 3)
75
-
-
dB
Group Delay
(Note 4)
-
25/Fs
-
s
De-emphasis Error (referenced to 1 kHz)
Fs = 32 kHz
Fs = 44.1 kHz
Fs = 48 kHz
-
-
-
-
-
-
+0.3/-0.3
+0.2/-0.4
+0.1/-0.45
dB
dB
dB
dc Accuracy
Interchannel Gain Mismatch
-
0.1
-
dB
Gain Error
-
2
5
%
Gain Drift
-
200
-
ppm/C
Power Supplies
Power Supply Current:
Normal Operation
Power-down
I
A
I
D
I
A
+I
D
-
-
-
-
30
12
42
500
-
-
45
-
mA
mA
mA
A
Power Dissipation
Normal Operation
Power-down
-
-
185
2.5
22.5
-
mW
mW
Power Supply Rejection Ratio (1 kHz)
PSRR
-
60
-
dB
CS4329
DS153F1
3
ANALOG CHARACTERISTICS (CONTINUED)
Notes: 1. Triangular PDF Dithered Data
2. AUTO-MUTE active. See parameter definitions
3. The passband and stopband edges scale with frequency. For input sample rates, Fs, other than 48 kHz,
the passband edge is 0.4535Fs and the stopband edge is 0.5465Fs.
4. Group Delay for Fs=48 kHz 25/48 kHz=520
s
5. Specified for a fully differential output ((AOUT+)-(AOUT-)). See Figure 12.
SWITCHING CHARACTERISTICS
(T
A
= -10 to 70C; Logic 0 = AGND = DGND; Logic 1 = VD = VA = 5.25
to 4.75 Volts; C
L
= 20 pF)
Parameter
Symbol Min Typ
Max
Unit
Analog Output
Differential Full Scale Output Voltage
(Note 5)
1.90
2.0
2.10
Vrms
Output Common Mode Voltage
-
2.2
-
V
Differential Offset
-
3
15
mV
AC Load Resistance
R
L
4
-
-
k
Load Capacitance
C
L
-
-
100
pf
Parameter
Symbol Min Typ
Max
Unit
Input Sample Rate
Fs
1
-
50
kHz
MCLK Pulse Width High
MCLK / LRCK = 512
10
-
-
ns
MCLK Pulse Width Low
MCLK / LRCK = 512
10
-
-
ns
MCLK Pulse Width High
MCLK / LRCK = 384
21
-
-
ns
MCLK Pulse Width Low
MCLK / LRCK = 384
21
-
-
ns
MCLK Pulse Width High
MCLK / LRCK = 256
31
-
-
ns
MCLK Pulse Width Low
MCLK / LRCK = 256
32
-
-
ns
External SCLK Mode
SCLK Pulse Width Low
t
sclkl
20
-
-
ns
SCLK Pulse Width High
t
sclkh
20
-
-
ns
SCLK Period
t
sclkw
-
-
ns
SCLK rising to LRCK edge delay
t
slrd
20
-
-
ns
SCLK rising to LRCK edge setup time
t
slrs
20
-
-
ns
SDATA valid to SCLK rising setup time
t
sdlrs
20
-
-
ns
SCLK rising to SDATA hold time
t
sdh
20
-
-
ns
Internal SCLK Mode
SCLK Period
SCLK / LRCK = 64
t
sclkw
-
-
ns
SDATA valid to SCLK rising setup time
t
sdlrs
-
-
ns
SCLK rising to SDATA hold time
MCLK / LRCK = 256 or 512
t
sdh
-
-
ns
SCLK rising to SDATA hold time
MCLK / LRCK = 384
t
sdh
-
-
ns
1
128 Fs
( )
--------------------
1
64 Fs
( )
-----------------
1
512 Fs
( )
--------------------
10
+
1
512 Fs
( )
--------------------
15
+
1
384 Fs
( )
--------------------
15
+
CS4329
4
DS153F1
sclkh
t
slrs
t
slrd
t
sdlrs
t
sdh
t
sclkl
t
SDATA
SCLK
LRCK
SDATA
*INTERNAL SCLK
LRCK
sclkw
t
sdlrs
t
sdh
t
External Serial Mode Input Timing
Internal Serial Mode Input Timing
* The SCLK pin must be terminated to ground.
The SCLK pulses shown are internal to the CS4329.
CS4329
DS153F1
5
DIGITAL CHARACTERISTICS
(T
A
= 25C; VD = 5 V 5%)
ABSOLUTE MAXIMUM RATINGS
(AGND = 0 V, all voltages with respect to ground.)
WARNING: Operation at or beyond these limits may result in permanent damage to the device.Normal operation is
not guaranteed at these extremes.
RECOMMENDED OPERATING CONDITIONS
(DGND = 0V; all voltages with respect to ground)
Parameter
Symbol Min Typ
Max
Unit
High-Level Input Voltage
V
IH
2.0
-
-
V
Low-Level Input Voltage
V
IL
-
-
0.8
V
Input Leakage Current
V
in
-
-
10.0
A
Digital Input Capacitance
-
10
-
pF
Parameter
Symbol Min
Max
Unit
DC Power Supply:
Positive Analog
Positive Digital
|VA - VD|
VA
VD
-0.3
-0.3
0.0
6.0
6.0
0.4
V
V
V
Input Current, Any Pin Except Supplies
I
in
-
10
mA
Digital Input Voltage
V
IND
-0.3
(VD)+0.4
V
Ambient Operating Temperature (power applied)
T
A
-55
125
C
Storage Temperature
T
stg
-65
150
C
Parameter
Symbol Min Typ
Max
Unit
DC Power Supply:
Positive Digital
Positive Analog
|VA - VD|
VD
VA
4.75
4.75
-
5.0
5.0
-
5.25
5.25
0.4
V
V
V
CS4329
6
DS153F1
SCLK*
Audio
Data
Processor
External Clock
MCLK
AGND
AOUTR+
CS4329
SDATA
VA
AOUTR-
+5V
Analog
10
0.1
F
+ 1
F
DEM0
DEM1
Mode
Select
DIF1
DIF0
AOUTL-
AOUTL+
DGND
VD
MUTE_R
MUTE_L
AUTO_MUTE
Analog
Conditioning
Analog
Conditioning
6
3
17
18
13
14
4
5
8
11
16
15
2
1
10
9
7
12
19
20
DIF2
LRCK
* SCLK must be connected to DGND
for operation in Internal SCLK Mode
0.1
F
+ 1
F
Figure 1. Typical Connection Diagram
CS4329
DS153F1
7
GENERAL DESCRIPTION
The CS4329 is a complete stereo digital-to-analog
system including 128 digital interpolation, fourth-
order delta-sigma digital-to-analog conversion,
128 oversampled one-bit delta-sigma modulator
and analog filtering. This architecture provides a
high insensitivity to clock jitter. The DAC converts
digital data at any input sample rate between 1 and
50 kHz, including the standard audio rates of 48,
44.1 and 32 kHz.
The primary purpose of using delta-sigma modula-
tion techniques is to avoid the limitations of laser
trimmed resistive DAC architectures by using an
inherently linear 1-bit DAC. The advantages of a 1-
bit DAC include: ideal differential linearity, no dis-
tortion mechanisms due to resistor matching errors
and no linearity drift over time and temperature due
to variations in resistor values.
Digital Interpolation Filter
The digital interpolation filter increases the sample
rate by a factor of 4 and is followed by a 32 digital
sample-and hold to effectively achieve a 128 in-
terpolation filter. This filter eliminates images of
the baseband audio signal which exist at multiples
of the input sample rate, Fs. This allows for the se-
lection of a less complex analog filter based on out-
of-band noise attenuation requirements rather than
anti-image filtering. Following the interpolation
filter, the resulting frequency spectrum has images
of the input signal at multiples of 128 the input
sample rate. These images are removed by the ex-
ternal analog filter.
Delta-Sigma Modulator
The interpolation filter is followed by a fourth-or-
der delta-sigma modulator which converts the 24-
bit interpolation filter output into 1-bit data at
128 Fs.
Switched-Capacitor Filter
The delta-sigma modulator is followed by a digital-
to-analog converter which translates the 1-bit data
into a series of charge packets. The magnitude of
the charge in each packet is determined by sam-
pling of a voltage reference onto a switched capac-
itor, where the polarity of each packet is controlled
by the 1-bit signal. This technique greatly reduces
the sensitivity to clock jitter and is a major im-
provement over earlier generations of 1-bit digital-
to-analog converters where the magnitude of
charge in the D-to-A process is determined by
switching a current reference for a period of time
defined by the master clock.
The CS4329 incorporates a differential output to
maximize the output level to minimize the amount
of gain required in the output analog stage. The dif-
ferential output also allows for the cancellation of
common mode errors in the differential to singled-
ended converter.
Interpolator
Delta-Sigma
Modulator
DAC
Analog
Low-Pass
Filter
AOUTL+
AOUTL-
Figure 2. Block Diagram
CS4329
8
DS153F1
SYSTEM DESIGN
Master Clock
The Master Clock, MCLK, is used to operate the
digital interpolation filter and the delta-sigma mod-
ulator. MCLK must be either 256, 384 or 512
the desired Input Sample Rate, Fs. Fs is the fre-
quency at which digital audio samples for each
channel are input to the DAC and is equal to the
LRCK frequency. The MCLK to LRCK frequency
ratio is detected automatically during the initializa-
tion sequence by counting the number of MCLK
transitions during a single LRCK period. Internal
dividers are then set to generate the proper clocks
for the digital filter, delta-sigma modulator and
switched-capacitor filter. LRCK must be synchro-
nous with MCLK. Once the MCLK to LRCK fre-
quency ratio has been detected, the phase and
frequency relationship between the two clocks
must remain fixed. If during any LRCK this rela-
tionship is changed, the CS4329 will reset. Table 1
illustrates the standard audio sample rates and the
required MCLK frequencies.
Table 1. Common Clock Frequencies
Serial Data Interface
The Serial Data interface is accomplished via the
serial data input, SDATA, serial data clock, SCLK,
and the left/right clock, LRCK. The CS4329 sup-
ports seven serial data formats which are selected
via the digital input format pins DIF0, DIF1 and
DIF2. The different formats control the relation-
ship of LRCK to the serial data and the edge of
SCLK used to latch the data into the input buffer.
Table 2 lists the seven formats, along with the asso-
ciated figure number. The serial data is represented
in 2's-complement format with the MSB-first in all
seven formats.
Formats 0, 1 and 2 are shown in Figure 3. The audio
data is right-justified, LSB aligned with the trailing
edge of LRCK, and latched into the serial input
data buffer on the rising edge of SCLK. Formats 0,
1 and 2 are 16, 18 and 20-bit versions and differ
only in the number of data bits required.
Formats 3 and 4 are 20-bit left justified, MSB
aligned with the leading edge of LRCK, and are
identical with the exception of the SCLK edge used
to latch data. Data is latched on the falling edge of
SCLK in Format 3 and the rising edge of SCLK in
Format 4. Both formats will support 16 and 18-bit
inputs if the data is followed by four or two zeros to
simulate a 20-bit input as shown in Figures 4 and 5.
A very small offset will result if the 18 or 16-bit
data is followed by static non-zero data.
Formats 5 and 6 are compatible with the I
2
S serial
data protocol and are shown in Figures 6 and 7. No-
tice that the MSB is delayed 1 period of SCLK fol-
lowing the leading edge of LRCK and LRCK is
inverted compared to the previous formats. Data is
latched on the rising edge of SCLK. Format 5 is 16-
bit I
2
S while Format 6 is 20-bit I
2
S. 18-bit I
2
S can
be implemented in Format 6 if the data is followed
by two zeros to simulate a 20-bit input as shown in
Figure 7. A very small offset will result if the 18-bit
data is followed by static non-zero data.
Table 2. Digital Input Formats
Fs
(kHz)
MCLK (MHz)
256x
384x
512x
32
8.1920
12.2880
16.3840
44.1
11.2896
16.9344
22.5792
48
12.2880
18.4320
24.5760
DIF2
DIF1
DIF0
Format
Figure
0
0
0
0
3
0
0
1
1
3
0
1
0
2
3
0
1
1
3
4
1
0
0
4
5
1
0
1
5
6
1
1
0
6
7
1
1
1
Calibrate
-
CS4
329
DS153F
1
9
LRCK
SCLK
Right Channel
SDATA
Format 1
0
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
SDATA
Format 2
0
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
17 16
SDATA
Format 0
0
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
Left Channel
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
6
5
4
3
2
1
0
9 8
7
15 14 13 12 11 10
17 16
17 16
19 18
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
16
17
18
19
NOTE: Format 1 is not compatible with CS4390
Figure 3. Digital Input Format 0, 1 and 2.
LRCK
SCLK
Left Channel
Right Channel
SDATA
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
18-Bit
SDATA
20-Bit
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
17 16
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
17 16
17
19
17 16
19 18
19 18
17 16
SDATA
4
3
2
1
0
7
6
5
13 12 11 10 9
8
6
5
4
3
2
1
0
9
8
7
13 12 11 10
16-Bit
15
15 14
15 14
Figure 4. Digital Input Format 3.
CS4
329
10
DS153F1
LRCK
SCLK
Left Channel
Right Channel
SDATA
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
18-Bit
SDATA
20-Bit
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
17 16
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
17 16
17
19
17 16
19 18
19 18
17 16
SDATA
4
3
2
1
0
7
6
5
13 12 11 10 9
8
6
5
4
3
2
1
0
9
8
7
13 12 11 10
16-Bit
15
15 14
15 14
Figure 5. Digital Input Format 4.
LRCK
SCLK
Left Channel
Right Channel
SDATA
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
16-Bit
15
Figure 6. Digital Input Format 5.
LRCK
SCLK
Left Channel
Right Channel
SDATA
18-Bit
SDATA
20-Bit
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
17 16
6
5
4
3
2
1
0
9
8
7
15 14 13 12 11 10
17 16
17
19
17 16
19 18
19 18
17 16
Figure 7. Digital Input Format 6.
CS4329
DS153F1
11
Serial Clock
The serial clock controls the shifting of data into
the input data buffers. The CS4329 supports both
external and internal serial clock generation modes.
External Serial Clock
The CS4329 will enter the external serial clock
mode if 15 or more high\low transitions are detect-
ed on the SCLK pin during any phase of the LRCK
period. When this mode is enabled, internal serial
clock mode cannot be accessed without returning
to the power down mode.
Internal Serial Clock
In the Internal Serial Clock Mode, the serial clock
is internally derived and synchronous with MCLK.
The internal SCLK / LRCK ratio is always 64 and
operation in this mode is identical to operation with
an external serial clock synchronized with LRCK.
The SCLK pin must be connected to DGND for
proper operation.
The internal serial clock mode is advantageous in
that there are situations where improper serial
clock routing on the printed circuit board can de-
grade system performance. The use of the internal
serial clock mode simplifies the routing of the
printed circuit board by allowing the serial clock
trace to be deleted and avoids possible interference
effects.
Mute Functions
The CS4329 includes an auto-mute function which
will initiate a mute if 8192 consecutive 0's or 1's are
input on both the Left and Right channels. The
mute will be released when non-static input data is
applied to the DAC. The auto-mute function is use-
ful for applications, such as compact disk players,
where the idle channel noise must be minimized.
This feature is active only if the AUTO_MUTE pin
is low and is independent of the status of MUTE_L
and MUTE_R. Either channel can also be muted
instantaneously with the MUTE_L or MUTE_R.
De-Emphasis
Implementation of digital de-emphasis requires re-
configuration of the digital filter to maintain the fil-
ter response shown in Figure 8 at multiple sample
rates. The CS4329 is capable of digital de-empha-
sis for 32, 44.1 or 48kHz sample rates. Table 3
shows the de-emphasis control inputs for DEM 0
and DEM 1.
Table 3. De-Emphasis Filter Selection
Initialization, Calibration and Power-Down
Upon initial power-up, the DAC enters the power-
down mode. The interpolation filters and delta-sig-
ma modulators are reset, and the internal voltage
reference, one-bit D/A converters and switched-ca-
pacitor low-pass filters are powered down. The de-
vice will remain in the power-down mode until
MCLK and LRCK are presented. Once MCLK and
LRCK are detected, MCLK occurrences are count-
ed over one LRCK period to determine the
MCLK/LRCK frequency ratio. The phase and fre-
quency relationship between the two clocks must
remain fixed. If during any LRCK this relationship
DEM 1
DEM 0
De-emphasis
0
0
32 kHz
0
1
44.1 kHz
1
0
48 kHz
1
1
OFF
Gain
dB
-10dB
0dB
Frequency
T2 = 15
s
T1=50
s
F1
3.183 kHz
F2
10.61 kHz
Figure 8. De-emphasis Filter Response
CS4329
12
DS153F1
is changed, the CS4390 will reset. Power is applied
to the internal voltage reference, the D/A convert-
ers, switched-capacitor filters and the DAC will
then enter a calibration mode to properly set the
common mode bias voltage and minimize the dif-
ferential offset. This initialization and calibration
sequence requires approximately 2700 cycles of
LRCK.
A offset calibration can also be invoked by taking
the Format select pins, DIF0, DIF1 and DIF2, to a
logic 1 as shown in Table 2. During calibration, the
differential outputs are shorted together and the
common-mode voltage appears at the output with
approximately an 8 kohm output impedance. Fol-
lowing calibration, the analog output impedance
becomes less than 10 ohms and the common mode
voltage will move to approximately 2.2 V .
The CS4329 will enter the power-down mode,
within 1 period of LRCK, if either MCLK or
LRCK is removed. The initialization sequence, as
described above, occurs when MCLK and LRCK
are restored.
Combined Digital and Analog Filter
Response
The frequency response of the combined analog
switched-capacitor and digital filters is shown in
Figures 9, 10 and 11. The overall response is clock
dependent and will scale with Fs. Note that the re-
sponse plots have been normalized to Fs and can be
de-normalized by multiplying the X-axis scale by
Fs, such as 48 kHz.
Analog Output and Filtering
The analog output should be operated in a differen-
tial mode which allows for the cancellation of com-
mon mode errors including noise, distortion and
offset voltage. Each output will produce a nominal
2.83 Vpp (1 Vrms) output for a full scale digital in-
put which equates to a 5.66 Vpp (2Vrms) differen-
tial signal as shown in Figure 12.
0
-10
-20
-30
-40
-50
-60
-70
-80
-90
-100
0.0
0.1
0.2 0.3
0.4
0.5
0.6
0.7 0.8
0.9
1.0
Frequency (x Fs)
M
a
gn
it
ude
(
d
B)
Figure 9. CS4329 Combined Digital and Analog Filter
Stopband Rejection
0
-10
-20
-30
-40
-50
-60
-70
-80
-90
-100
0.45
0.48
0.51
0.54
0.57
0.60
M
a
gni
t
u
de (
d
B
)
Frequency (x Fs)
Figure 10. CS4329 Combined Digital and Analog
Filter
0
-1
-2
-3
-4
-5
-6
-7
-8
-9
-10
0.46
0.47
0.48
0.49
0.50
0.51
0.52
M
agn
it
u
d
e
(
d
B)
Frequency (x Fs)
Figure 11. Combined Digital and Analog Filter
CS4329
DS153F1
13
Figure 13 displays the CS4329 output noise spec-
trum. The noise beyond the audio band can be fur-
ther reduced with additional analog filtering. The
applications note "Design Notes for a 2-Pole Filter
with Differential Input " discusses the second-order
Butterworth filter and differential to signal-ended
converter which was implemented on the CS4329
evaluation board, CDB4329. The CS4329 filter is a
linear phase design and does not include phase or
amplitude compensation for an external filter.
Therefore, the DAC system phase and amplitude
response will be dependent on the external analog
circuitry.
Grounding and Power Supply Decoupling
As with any high resolution converter, the CS4329
requires careful attention to power supply and
grounding arrangements to optimize performance.
Figure 1 shows the recommended power arrange-
ments with VA connected to a clean +5volt supply.
VD should be derived from VA through a 10
re-
sistor. VD should not be used to power additional
digital circuitry. All mode pins which require VD
should be connected to pin 6 of the CS4329. All
mode pins which require DGND should be con-
nected to pin 5 of the CS4329. Pins 4 and 5, AGND
and DGND, should be connected together at the
CS4329. DGND for the CS4329 should not be con-
fused with the ground for the digital section of the
system. The CS4329 should be positioned over the
analog ground plane near the digital/analog ground
plane split. The analog and digital ground planes
must be connected elsewhere in the system. The
CS4329 evaluation board, CDB4329, demonstrates
this layout technique. This technique minimizes
digital noise and insures proper power supply
matching and sequencing. Decoupling capacitors
should be located as near to the CS4329 as possi-
ble.
Performance Plots
The following collection of CS4329 measurement
plots were taken from the CDB4329 evaluation
board using the Audio Precision Dual Domain Sys-
tem Two.
Figure 14 shows the frequency response at a
48 kHz sample rate. The response is flat to 20 kHz
+/-0.1 dB as specified.
Figure 15 shows THD+N versus signal amplitude
for a 1 kHz 20-bit dithered input signal. Notice that
the there is no increase in distortion as the signal
level decreases. This indicates very good low-level
linearity, one of the key benefits of delta-sigma
digital to analog conversion.
Figure 16 shows a 16 k FFT of a 1 kHz full-scale
input signal. The signal has been filtered by a notch
filter within the System Two to remove the funda-
mental component of the signal. This minimizes
the distortion created in the analyzer analog-to-dig-
ital converter. This technique is discussed by Audio
CS4329
AOUT+
AOUT-
Full Scale Input level= (AIN+) - (AIN-)= 5.66 Vpp
(2.2 + 1.4)V
2.2V
(2.2 - 1.4)V
(2.2 + 1.4)V
2.2V
(2.2 - 1.4)V
Figure 12. Full Scale Input Voltage
0
-20
-40
-60
-80
-100
-120
-140
-160
0
.25 .50
.75 1.00 1.25 1.50 1.75 2.00 2.25 2.50
M
agn
it
ud
e
(dB)
Frequency (x Fs)
Figure 13. CS4329 Output Noise Spectrum
CS4329
14
DS153F1
Precision in the 10th anniversary addition of AU-
DIO.TST.
Figure 17 shows a 16 k FFT of a 1 kHz -20 dBFS
input signal. The signal has been filtered by a notch
filter within the System Two to remove the funda-
mental component of the signal.
Figure 18 shows a 16 k FFT of a 1 kHz -60 dBFS
input signal.
Figure 19 shows the fade-to-noise linearity. The in-
put signal is a dithered 20-bit 500 Hz sine wave
which fades from -60 to -120 dBFS. During the
fade, the output from the CS4329 is measured and
compared to the ideal level. Notice the very close
tracking of the output level to the ideal, even at low
level inputs. The gradual shift of the plot away
from zero at signals levels < -110 dB is caused by
the background noise starting to dominate the mea-
surement.
CS4329
DS153F1
15
20
20k
50
100
200
500
1k
2k
5k
10k
Hz
-1
+1
-0.8
-0.6
-0.4
-0.2
+0
+0.2
+0.4
+0.6
+0.8
d
B
r
A
-60
+0
-50
-40
-30
-20
-10
dBFS
-120
-60
-115
-110
-105
-100
-95
-90
-85
-80
-75
-70
-65
d
B
r
A
Figure 14. Frequency Response
Figure 15. THD+N vs. Amplitude
2.5k
20k
5k
7.5k
10k
12.5k
15k
17.5k
Hz
-160
+0
-150
-140
-130
-120
-110
-100
-90
-80
-70
-60
-50
-40
-30
-20
-10
d
B
r
A
2.5k
20k
5k
7.5k
10k
12.5k
15k
17.5k
Hz
-160
+0
-150
-140
-130
-120
-110
-100
-90
-80
-70
-60
-50
-40
-30
-20
-10
d
B
r
A
Figure 16. 0 dBFS FFT
Figure 17. -20 dBFS FFT
-120
+0
-100
-80
-60
-40
-20
dBFS
-5
+5
-4
-3
-2
-1
-0
+1
+2
+3
+4
d
B
r
A
2k
20k
4k
6k
8k
10k
12k
14k
16k
18k
Hz
-150
+0
-140
-130
-120
-110
-100
-90
-80
-70
-60
-50
-40
-30
-20
-10
d
B
r
A
Figure 18. -60 dBFS FFT
Figure 19. Fade-to-Noise Linearity
CS4329
16
DS153F1
PIN DESCRIPTIONS
Power Supply Connections
VA - Positive Analog Power, PIN 3.
Positive analog supply. Nominally +5 volts.
VD - Positive Digital Power, PIN 6.
Positive supply for the digital section. Nominally +5 volts.
AGND - Analog Ground, PIN 4.
Analog ground reference.
DGND - Digital Ground, PIN 5.
Digital ground for the digital section.
Analog Outputs
AOUTR+,AOUTR- - Differential Right Channel Analog Outputs, PIN 14, PIN 13.
Analog output connections for the Right channel differential outputs. Nominally 2 Vrms
(differential) for full-scale digital input signal.
AOUTL+,AOUTL- - Differential Left Channel Analog Outputs, PIN 18, PIN 17.
Analog output connections for the Left channel differential outputs. Nominally 2 Vrms
(differential) for full-scale digital input signal.
1
2
3
4
5
6
7
8
9
20
19
18
17
16
15
14
13
12
10
11
DEM0
DEM1
VA
AGND
DGND
VD
LRCK
MCLK
SCLK
SDATA
DIF0
DIF11
AOUTL+
AOUTL-
MUTE_L
MUTE_R
AOUTR+
AOUTR-
DIF2
AUTO-MUTE
PDIP and SSOP
CS4329
DS153F1
17
Digital Inputs
MCLK - Clock Input, PIN 8.
The frequency must be either 256, 384 or 512 the input sample rate (Fs).
LRCK - Left/Right Clock, PIN 7.
This input determines which channel is currently being input on the Serial Data Input pin,
SDATA. The format of LRCK is controlled by DIF0, DIF1 and DIF2.
SCLK - Serial Bit Input Clock, PIN 9.
Clocks the individual bits of the serial data in from the SDATA pin. The edge used to latch
SDATA is controlled by DIF0, DIF1 and DIF2.
SDATA - Serial Data Input, PIN 10.
Two's complement MSB-first serial data of either 16, 18 or 20 bits is input on this pin. The
data is clocked into the CS4329 via the SCLK clock and the channel is determined by the
LRCK clock. The format for the previous two clocks is determined by the Digital Input Format
pins, DIF0, DIF1 and DIF2.
DIF0, DIF1, DIF2 - Digital Input Format, PINS 20, 19, 12
These three pins select one of seven formats for the incoming serial data stream. These pins set
the format of the SCLK and LRCK clocks with respect to SDATA. The formats are listed in
Table 2.
DEM0, DEM1 - De-Emphasis Select, PINS 1, 2.
Controls the activation of the standard 50/15us de-emphasis filter for either 32, 44.1 or 48 kHz
sample rates.
AUTO-MUTE - Automatic Mute on Zero-Data, PIN 11.
When Auto-Mute is low the analog outputs are muted following 8192 consecutive LRCK
cycles of static 0 or 1 data. Mute is canceled with the return of non-static input data.
MUTE_R , MUTE_L Mute, PINS 15, 16.
MUTE_L low activates a muting function for the Left channel. MUTE_R low activates a
muting function for the Right channel.
CS4329
18
DS153F1
PARAMETER DEFINITIONS
Dynamic Range
The ratio of the full scale rms value of the signal to the rms sum of all other spectral
components over the specified bandwidth. Dynamic range is a signal-to-noise measurement
over the specified bandwidth made with a -60 dBFS signal. 60 dB is then added to the resulting
measurement to refer the measurement to full scale. This technique ensures that the distortion
components are below the noise level and do not effect the measurement. This measurement
technique has been accepted by the Audio Engineering Society, AES17-1991, and the
Electronic Industries Association of Japan, EIAJ CP-307.
Total Harmonic Distortion + Noise
The ratio of the rms value of the signal to the rms sum of all other spectral components over
the specified bandwidth (typically 10 Hz to 20 kHz), including distortion components.
Expressed in decibels.
Idle Channel Noise / Signal-to-Noise-Ratio
The ratio of the rms analog output level with 1kHz full scale digital input to the rms analog
output level with all zeros into the digital input. Measured A-weighted over a 10 Hz to 20 kHz
bandwidth. Units in decibels. This specification has been standardized by the Audio
Engineering Society, AES17-1991, and referred to as Idle Channel Noise. This specification has
also been standardized by the Electronic Industries Association of Japan, EIAJ CP-307, and
referred to as Signal-to-Noise-Ratio.
Interchannel Isolation
A measure of crosstalk between the left and right channels. Measured for each channel at the
converter's output with all zeros to the input under test and a full-scale signal applied to the
other channel. Units in decibels.
Frequency Response
A measure of the amplitude response variation from 10 Hz to 20 kHz relative to the amplitude
response at 1 kHz. Units in decibels.
De-Emphasis Error
A measure of the difference between the ideal de-emphasis filter and the actual de-emphasis
filter response. Measured from 10 Hz to 20 kHz relative to 1 kHz. Units in decibels.
Interchannel Gain Mismatch
The gain difference between left and right channels. Units in decibels.
Gain Error
The deviation from the nominal full scale analog output for a full scale digital input.
Gain Drift
The change in gain value with temperature. Units in ppm/C.
CS4329
DS153F1
19
PACKAGE DIMENSIONS
Notes: 1. "D" and "E1" are reference datums and do not included mold flash or protrusions, but do include mold
mismatch and are measured at the parting line, mold flash or protrusions shall not exceed 0.20 mm per
side.
2. Dimension "b" does not include dambar protrusion/intrusion. Allowable dambar protrusion shall be
0.13 mm total in excess of "b" dimension at maximum material condition. Dambar intrusion shall not
reduce dimension "b" by more than 0.07 mm at least material condition.
3. These dimensions apply to the flat section of the lead between 0.10 and 0.25 mm from lead tips.
INCHES
MILLIMETERS
NOTE
DIM
MIN
MAX
MIN
MAX
A
--
0.084
--
2.13
A1
0.002
0.010
0.05
0.25
A2
0.064
0.074
1.62
1.88
b
0.009
0.015
0.22
0.38
2,3
D
0.272
0.295
6.90
7.50
1
E
0.291
0.323
7.40
8.20
E1
0.197
0.220
5.00
5.60
1
e
0.022
0.030
0.55
0.75
L
0.025
0.041
0.63
1.03
0
8
0
8
20L SSOP PACKAGE DRAWING
E
N
1 2 3
e
b
2
A1
A2
A
D
SEATING
PLANE
E1
1
L
SIDE VIEW
END VIEW
TOP VIEW
CS4329
20
DS153F1
INCHES
MILLIMETERS
DIM
MIN
MAX
MIN
MAX
A 0.000
0.210
0.00
5.33
A1
0.015
0.025
0.38
0.64
A2
0.115
0.195
2.92
4.95
b
0.014
0.022
0.36
0.56
b1
0.045
0.070
1.14
1.78
c
0.008
0.014
0.20
0.36
D
0.980
1.060
24.89
26.92
E
0.300
0.325
7.62
8.26
E1
0.240
0.280
6.10
7.11
e
0.090
0.110
2.29
2.79
eA
0.280
0.320
7.11
8.13
eB
0.300
0.430
7.62
10.92
eC
0.000
0.060
0.00
1.52
L
0.115
0.150
2.92
3.81
0
15
0
15
20 PIN PLASTIC (PDIP) PACKAGE DRAWING
E1
D
SEATING
PLANE
b1
e
b
A
L
A1
TOP VIEW
BOTTOM VIEW
SIDE VIEW
1
eA
c
A2
E
eC
eB
Preliminary Product Information
This document contains information for a new product.
Cirrus Logic reserves the right to modify this product without notice.
21
Copyright
Cirrus Logic, Inc. 1997
(All Rights Reserved)
Cirrus Logic, Inc.
Crystal Semiconductor Products Division
P.O. Box 17847, Austin, Texas 78760
(512) 445 7222 FAX: (512) 445 7581
http://www.crystal.com
CDB4329
CDB4390
Evaluation Board for CS4329 and CS4390
Features
l
Demonstrates recommended layout
and grounding arrangements
l
CS8412 Receives AES/EBU, S/PDIF,
& EIAJ-340 Compatible Digital Audio
l
Digital and Analog Patch Areas
l
Requires only a digital signal source
and power supplies for a complete Digital-to-
Analog-Converter system
Description
The CDB4329/90 evaluation board is an excellent
means for quickly evaluating the CS4329 or CS4390 24-
bit, stereo D/A converter. Evaluation requires an analog
signal analyzer, a digital signal source and a power sup-
ply. Analog outputs are provided via RCA connectors for
both channels.
The CS8412 digital audio receiver I.C. provides the sys-
tem timing necessary to operate the CS4329/90 and will
accept AES/EBU, S/PDIF, and EIAJ-340 compatible
audio data. The evaluation board may also be config-
ured to accept external timing signals for operation in a
user application during system development.
ORDERING INFO
CDB4329
CDB4390
I
I/O for
Clocks
and Data
CS8412
Digital
Audio
Interface
CS4329
or
CS4390
Analog
Filter
NOV `97
DS153DB3
CDB4329 CDB4390
22 DS153DB3
CDB4329/90 SYSTEM OVERVIEW
The CDB4329/90 evaluation board is an excellent
means of quickly evaluating the CS4329/90. The
CS8412 digital audio interface receiver provides an
easy interface to digital audio signal sources in-
cluding the majority of digital audio test equip-
ment. The evaluation board also allows the user to
supply clocks and data through a 10-pin header for
system development.
The CDB4329/90 schematic has been partitioned
into 8 schematics shown in Figures 2 through 9.
Each partitioned schematic is represented in the
system diagram shown in Figure 1. Notice that the
system diagram also includes the interconnections
between the partitioned schematics.
CS4329/90 Digital to Analog Converter
A description of the CS4329 or CS4390 is included
in the CS4329 and CS4390 data sheets.
CS8412 Digital Audio Receiver
The system receives and decodes the standard
S/PDIF data format using a CS8412 Digital Audio
Receiver, Figure 9. The outputs of the CS8412 in-
clude a serial bit clock, serial data, left-right clock
(FSYNC), de-emphasis control and a 256Fs master
clock.
During normal operation, the CS8412 operates in
the Channel Status mode where the LED's display
channel status information for the channel selected
by the CSLR/FCK jumper. This allows the CS8412
to decode and supply the de-emphasis bit from the
digital audio interface for control of the CS4329/90
de-emphasis filter via pin 3, CC/F0, of the CS8412.
When the Error Information Switch is activated,
the CS8412 operates in the Error and Frequency in-
formation mode. The information displayed by the
LED's can be decoded by consulting the CS8412
data sheet. If the Error Information Switch is acti-
vated, the CC/F0 output has no relation to the de-
emphasis bit and it is likely that the de-emphasis
control for the CS4329/90 will be erroneous and
produce an incorrect audio output.
Encoded sample frequency information can be dis-
played provided a proper clock is being applied to
the FCK pin of the CS8412. When an LED is lit,
this indicates a "1" on the corresponding pin locat-
ed on the CS8412. When an LED is off, this indi-
cates a "0" on the corresponding pin. Neither the L
or R option of CSLR/FCK should be selected if the
FCK pin is being driven by a clock signal.
The evaluation board has been designed such that
the input can be either optical or coax, Figure 8. It
is not necessary to select the active input. However,
both inputs can not be driven simultaneously.
Data Format
The CS4329/90 must be configured to be compati-
ble with the incoming data and can be set with
DIF0, DIF1, and DIF2. The CS8412 data format
can be set with the M0, M1, M2 and M3. There are
several data formats which the CS8412 can pro-
duce that are compatible with CS4329/90. Refer to
Table 2 for one possibility.
Power Supply Circuitry
Power is supplied to the evaluation board by four
binding posts, Figure 10. The +5 Volt input sup-
plies power to the CS4329/90 (through VA+), the
CS8412 (through VA+ and VD+), and the +5 Volt
digital circuitry (through VD+). The 12 volt input
supplies power to the analog filter circuitry.
Input/Output for Clocks and Data
The evaluation board has been designed to allow
the interface to external systems via the 10-pin
header, J1. This header allows the evaluation board
to accept externally generated clocks and data. The
schematic for the clock/data I/O is shown in Figure
7. The 74HC243 transceiver functions as an I/O
buffer where the CLK SOURCE jumper deter-
mines if the transceiver operates as a transmitter or
receiver.
CDB4329 CDB4390
DS153DB3 23
The transceiver operates as a transmitter with the
CLK SOURCE jumper in the 8412 position.
LRCK, SDATA, and SCLK from the CS8412 will
be available on J1. J22 must be in the 0 position and
J23 must be in the 1 position for MCLK to be an
output and to avoid bus contention on MCLK.
The transceiver operates as a receiver with the CLK
SOURCE jumper in the EXTERNAL position.
LRCK, SDATA and SCLK on J1 become inputs.
The CS8412 must be removed from the evaluation
board for operation in this mode.
There are 2 options for the source of MCLK in the
EXT CLK source mode. MCLK can be an input
with J23 in the 1 position and J22 in the 0 position.
However, the recommended mode of operation is
to generate MCLK on the evaluation board. MCLK
becomes an output with LRCK, SCLK and SDA-
TA inputs. This technique insures that the
CS4329/90 receives a jitter free clock to maximize
performance. This can be accomplished by install-
ing a crystal oscillator into U4, see Figure 9 (the
socket for U4 is located within the footprint for the
CS8412) and placing J22 in the 1 position and J23
in the 0 position.
Analog Filter
The design of the second-order Butterworth low-
pass filter, Figure 6, is discussed in the CS4329 and
CS4390 data sheets and the applications note "De-
sign Notes for a 2-pole Filter with Differential In-
put."
Grounding and Power Supply Decoupling
The CS4329/90 requires careful attention to power
supply and grounding arrangements to optimize
performance. The recommended power arrange-
ments would be VA+ connected to a clean +5 Volt
supply. The voltage VD+ (pin 6 of the CS4329/90)
should be derived from VA+ through a 2 ohm resis-
tor and should not used for any additional digital
circuitry. Ideally, mode pins which require this
voltage should be connected directly to VD+ (pin 6
of the CS4329/90) and mode pins which require
DGND should be connected directly to pin 5 of the
CS4329/90. AGND and DGND, Pins 4 and 5, are
connected together at the CS4329/90. However, it
was not possible to connect VD+ (pin 6 of the
CS4329/90) and DGND to the mode pins on the
CDB4329/90 due to layout complications resulting
from the hardware selected to exercise the features
of the CS4329/90.
Figure 2 shows the CS4329/90 and connections.
The evaluation board has separate analog and digi-
tal regions with individual ground planes. DGND
for the CS4329/90 should not be confused with the
ground for the digital section of the system (GND).
The CS4329/90 is positioned over the analog
ground plane near the digital/analog ground plane
split. These ground planes are connected elsewhere
on the board. This layout technique is used to min-
imize digital noise and to insure proper power sup-
ply matching/sequencing. The decoupling
capacitors are located as close to the CS4329/90 as
possible. Extensive use of ground plane fill on both
the analog and digital sections of the evaluation
board yield large reductions in radiated noise ef-
fects.
CDB4329 CDB4390
24 DS153DB3
Table 1. System Connections
Notes: 1. * Default setting from factory
Table 2. CDB4329/90 Jumper Selectable Options
CONNECTOR INPUT/OUTPUT SIGNAL PRESENT
+5V input +5 Volts for the CS4329/90, CS8412 and digital section
12V input 12 volts for analog filter section
GND input ground connection from power supply
Digital input input digital audio interface input via coax
Optical input input digital audio interface input via optical
J1 input/output I/O for system clocks and digital audio data
AOUTL output left channel analog output
AOUTR output right channel analog output
JUMPER PURPOSE POSITION FUNCTION SELECTED
CSLR/FCK Selects channel for
CS8412 channel status
information
L
R
See CS8412 data sheet for details
Clock Select Selects source of system
clocks and data
*8412
EXT
CS8412 clock/data source
External clock/data source
J22
J23
Selects MCLK as
input or output
0
1
See
Input/Output for Clocks and Data
section of
text
M0
M1
M2
M3
CS8412 mode select *Low
*Low
*Low
*Low
See CS8412 data sheet for details
auto_mute CS4329/90 Auto Mute *Low
High
On
Off
DEM0
DEM1
De-emphasis select *High
*Low
See CS4329 and CS4390 data sheets for details
set for 44.1 kHz
DIF0
DIF1
DIF2
CS4329/90 digital input
format
*High
*High
*Low
See CS4329 and CS4390 data sheets for details
SCLK CS4329/90 SCLK Mode *INT
EXT
Internal SCLK Mode
External SCLK Mode
DEM_8412 Selects source of de-
emphasis control
*Low
High
CS8412 de-emphasis
De-emphasis input static high
CDB4329 CDB4390
DS153DB3 25
Digital
Audio
Input
I/O for
Clocks
and Data
CS8412
Digital
Audio
Interface
RX
N
RX
P
MCLK
LRCK
SCLK
SDATA
CS4329
or
CS4390
AOUTL-
AOUTL+
AOUTR-
AOUTR+
Analog
Filter
DE
M0
DE
M1
De-emphasis
Mode
Mute
Section
Calibration and
Format Select
Section
AU
T
O
M
U
T
E
MU
T
E
_L
MUT
E
_
R
DI
F
0
DI
F
2
DI
F
1
Figure 1. System Block Diagram and Signal Flow
Fig 8 Fig 7
Fig 9 Fig 2
Fig 6
Fig 5
Fig 4
Fig 3
CDB4
32
9 CDB4
390
2
6
DS153DB3
Figure 2. CS4329/90 and Connections
CDB4329 CDB4390
DS153DB3 27
Figure 3. De-emphasis Circuitry
Figure 4. Mute Circuitry
Figure 5. Calibration and Format Select Circuitry
CDB4329 CDB4390
28 DS153DB3
NOTE: Rigth channel components in parentheses.
Figure 6. 2-pole Analog Filter
Figure 7. I/O Interface for Clocks and DATA
CDB4329 CDB4390
DS153DB3 29
OPTI Toshiba TORX173 optical receiver available from Insight Electronics
Figure 8. Digital Audio Input Circuit
CDB4
32
9 CDB4
390
3
0
DS153DB3
Note: U2 and U4 can not be installed simultaneously.
Figure 9. CS8412 and Connections
CDB4329 CDB4390
DS153DB3 31
Figure 10. Power Supply Connections
CDB4329 CDB4390
32 DS153DB3
Figure 11. CDB4329/90 Component Side Silkscreen
CDB4329 CDB4390
DS153DB3 33
Figure 12. CDB4329/90 Component Side (top)
CDB4329 CDB4390
34 DS153DB3
Figure 13. CDB4329/90 Solder Side (bottom)
Notes